Voltage fluctuation detection circuit

ABSTRACT

The present disclosure provides a voltage fluctuation detection circuit, which includes a rising edge trigger circuit and a detection and output circuit connected to an output terminal of the rising edge trigger circuit. When a change of the operating voltage within a preset clock period is greater than a preset bias voltage, an output signal of the output terminal undergoes at least one target flip between a high level and a low level. When the output signal of the rising edge trigger circuit always undergoes the target flips in N consecutive preset clock periods, and the operating voltage is always not less than a starting threshold value in each target flip of all the target flips in the N consecutive clock periods, the detection and output circuit generates an first signal, where N is a natural number not less than 2.

RELATED APPLICATION

The present application claims the benefit of priority to the Chinese patent application No. 202110690636.3, filed on Jun. 22, 2021, and entitled “Voltage Fluctuation Detection Circuit,” the entire content of which is incorporated herein by reference.

TECHNICAL FIELD

The present disclosure relates to the technical field of integrated circuits (ICs), and in particular to a voltage fluctuation detection circuit.

BACKGROUND

Switching power supplies are used in a wide variety of places. Smart phones, tablets, laptops, cameras and even some cars need to be charged with switching power supplies. Switching power supply can also supply power to clocks, radios, household audio amplifiers and other small appliances.

A switching power supply controller is an integrated circuit (IC) for controlling the switching power supply, which adjusts and/or controls the output of the switching power supply through specially designed circuits.

An AC-DC flyback controller is a switching power supply controller. The AC-DC flyback controller needs to detect the AC line voltage to determine when the AC line voltage is high enough to start the IC operation. When the AC line voltage is too low, the AC-DC flyback controller must stop switching operation to protect the system from excessive pressure during operation.

BRIEF SUMMARY

In order to solve the above-mentioned problems, the present disclosure provides a voltage fluctuation detection circuit. The voltage fluctuation detection circuit can detect the voltage of an AC line so as to determine whether the switching operation can be started or stopped.

The voltage fluctuation detection circuit includes: a rising edge trigger circuit, including an input terminal and an output terminal, where the rising edge trigger circuit detects an operating voltage received by the input terminal with a preset clock period, when a change of the operating voltage within the preset clock period is greater than a preset bias voltage, an output signal of the output terminal undergoes at least one target flip between a high level and a low level; and a detection and output circuit, connected to the output terminal of the rising edge trigger circuit, and configured to detect the change of the operating voltage and the target flip, and output a control signal according to a detection result, where when the detection result of the detection and output circuit indicates that an output signal of the rising edge trigger circuit always undergoes the target flip in N consecutive preset clock periods, and the operating voltage is always not less than a starting threshold value when each target flip of all the target flips occurring in the N consecutive preset clock periods, where the detection and output circuit generates an first signal, where N is a natural number not less than 2.

BRIEF DESCRIPTION OF THE DRAWINGS

The present disclosure will be further described based on exemplary embodiments. The above and other aspects of the embodiments of the present disclosure will become clearer in the following detailed description when read with reference to the drawings.

FIG. 1 illustrates a structure of a voltage fluctuation detection circuit according to some exemplary embodiments of the present disclosure;

FIG. 2A illustrates a timing diagram of various signals of the voltage rising edge detection circuit in operation according to some exemplary embodiments of the present disclosure;

FIG. 2B illustrates a timing diagram of V₁ and V₂ according to some exemplary embodiments of the present disclosure;

FIG. 2C is an enlarged view of curves of V₁ and V₂ in a clock period T₁ in FIG. 2B;

FIG. 2D is an enlarged view of curves of V₁ and V₂ in a clock period T₂ in FIG. 2B;

FIG. 2E is a detailed view of a region A in FIG. 2A according to the present disclosure;

FIG. 2F illustrates a timing diagram of various signals of a voltage rising edge detection circuit in operation according to some exemplary embodiments of the present disclosure;

FIG. 2G illustrates a structure of a detection and output circuit according to some exemplary embodiments of the present disclosure;

FIG. 3A illustrates a comparison between an input voltage and an output voltage of a voltage bias circuit according to some exemplary embodiments of the present disclosure;

FIG. 3B illustrates a comparison between a voltage on an output terminal of the voltage bias circuit and a second voltage applied to a second input terminal of a comparator according to some exemplary embodiments of the present disclosure;

FIG. 4A illustrates a comparison of outputs corresponding to two different inputs V_(HV) ¹ and V_(HV) ² under a constant ΔV according to some exemplary embodiments of the present disclosure;

FIG. 4B illustrates a relationship between the ΔV and a peak of V_(in) according to some exemplary embodiments of the present disclosure;

FIG. 4C illustrates a relationship between the ΔV and the peak of V_(in) according to some exemplary embodiments of the present disclosure;

FIG. 5 illustrates a structure of a voltage fluctuation detection circuit according to some exemplary embodiments of the present disclosure;

FIG. 6 illustrates a comparison between an operating voltage, a first voltage and a second voltage in the structure of the circuit shown in FIG. 5 ;

FIG. 7 illustrates a structure of a voltage fluctuation detection circuit according to some exemplary embodiments of the present disclosure; and

FIG. 8 illustrates a structure of a voltage fluctuation detection circuit according to some exemplary embodiments of the present disclosure.

DETAILED DESCRIPTION

The terms used herein are merely intended to describe specific examples or embodiments, rather than to limit the present disclosure. For example, unless contexts explicitly state otherwise, the singular forms “a”, “an” and “the” used herein may also include plural forms. In this disclosure, the terms “include” and/or “comprise” refer to the existence of an associated integer, step, operation, element, component and/or group, without excluding the existence of one or more other features, integers, steps, operations, elements, components and/or groups. In other words, other features, integers, steps, operations, elements, components and/or groups may be added to the system/method. In this disclosure, the term “A is on B” may mean that A is directly adjacent to B (above or below), or that A and B are indirectly adjacent (that is, A and B are separated by an object). The term “A is in B” may mean that A is completely in B or A is partially in B.

In the following description of the present disclosure, the economical efficiency of the features, the operation and function of related elements of the structure, as well as the combination and manufacturing of the components can be significantly improved. All of these aspects form part of the present disclosure with reference to the drawings. However, it should be understood that the drawings are merely intended for illustration purposes, rather than to limit the scope of the present disclosure.

In some exemplary embodiments, an IC needs a specially designed circuit(s) to detect the fluctuation of electrical signal. Generally, for example, an IC is only allowed to operate on the rising edge of an Alternating Current (AC) line. In this case, the premise of starting IC is that the AC must be on the rising edge. Therefore, in the design of a switching power supply circuit, it is necessary to design a special circuit to detect the voltage of an AC line.

In some exemplary embodiments, digital circuits may be used to sample and detect an AC line voltage in switching power supply circuit design. Since the switching power supply controller is usually an analog IC, adding digital design to the analog IC may increase the cost of the switching power supply controller.

The present disclosure provides a voltage fluctuation detection circuit. The voltage fluctuation detection circuit can detect the fluctuation of the electrical signal. The voltage fluctuation detection circuit provided by the application can achieve a balance among circuit complexity; detection accuracy and detection speed, and achieve the balance between optimal performance and IC cost. The voltage fluctuation detection circuit provided in this disclosure may be applied to all ICs for detecting the characteristics of electrical signals.

As an example, FIG. 1 illustrates a structure of a voltage fluctuation detection circuit 001 according to some exemplary embodiments of the present disclosure. As an example, FIG. 2A illustrates a timing diagram of various signals of the voltage rising edge detection circuit in operation according to some exemplary embodiments of the present disclosure. Specifically, the voltage fluctuation detection circuit 001 may include a rising edge trigger circuit 600 and a detection and output circuit 700. As an example, the rising edge trigger circuit 600 may include a voltage adjustment circuit 100 and a comparator 200. In some exemplary embodiments, the voltage fluctuation detection circuit 001 may further include a voltage divider circuit 400 and/or a latch circuit 800.

The voltage divider circuit 400 may include any circuit for dividing a signal V_(HV) input through a high voltage (HV) pin into an operating voltage signal V₀. For example, as shown in FIG. 1 , the voltage divider circuit 400 may include a first resistor R₁ and a second resistor R₂ connected in series. An output terminal 420 of the voltage divider circuit 400 may be connected between the first resistor R₁ and the second resistor R₂. One terminal of the voltage divider circuit 400 may be connected to the voltage input HV pin, and the other terminal thereof may be connected to a ground wire GND. In this way, by reasonably designing the resistance of the first resistor R₁ and the second resistor R₂, the voltage divider circuit 400 may divide the input voltage signal V_(HV) into the operating voltage signal V₀ at the output terminal 420.

The operating voltage signal V₀ may be an AC signal or a DC signal. For ease of description, in the following description of the present disclosure, the working mechanism of the voltage rising edge detection circuit 001 will be described by taking an AC voltage signal as the operating voltage signal. Referring to FIG. 2A, the operating voltage signal V₀ includes multiple periods, where the operating voltage signal in each period includes at least one rising edge and at least one falling edge. For ease of understanding, in the following description of the present disclosure, the working mechanism of the circuit provided by the present disclosure will be described by taking a mains AC signal without frequency modulation as the input signal V_(HV). The frequency f_(HV) of the input signal V_(HV) is 50 HZ, the same as that of the mains AC signal, that is, the period of the input signal V_(HV) is T_(HV)=20 ms. There are two rising edges and two falling edges in one period T_(HV) of the input signal V_(HV). The duration of one rising edge and one falling edge each is ¼ T_(HV).

The comparator 200 includes a first comparator input terminal 210, a second comparator input terminal 220 and a comparator output terminal 230. One of the first comparator input terminal 210 and the second comparator input terminal 220 may be a positive terminal (an input terminal marked with “+”) of the comparator 200, and the other may be a negative terminal (an input terminal marked with “−”) of the comparator 200. When the voltage of the positive terminal is higher than that of the negative terminal, the comparator output terminal comparator output terminal 230 of the comparator 200 outputs a high level. When the voltage of the negative terminal is higher than that of the positive terminal, the comparator output terminal comparator output terminal 230 of the comparator 200 outputs a low level. Taking FIG. 1 as an example, the first comparator input terminal 210 of the comparator may be electrically connected to a first output terminal 102 of the voltage adjustment circuit to receive a first voltage V₁. The second comparator input terminal 220 of the comparator may be electrically connected to a second output terminal 103 of the voltage adjustment circuit to receive a second voltage V₂. The comparator 200 may compare the magnitudes of the first voltage signal V₁ and the second voltage signal V₂, and output a high level or a low level via the comparator output terminal 230 according to a comparison result, that is, to output the comparison result between the first voltage V₁ and the second voltage V₂. When the first voltage signal V₁ is higher than the second voltage signal V₂, the comparator outputs a high level. When the first voltage signal V₁ is lower than the second voltage signal V₂, the comparator outputs a low level.

The detection and output circuit 700 is connected to the comparator output terminal 230. The detection and output circuit 700 detects the comparison result output by the comparator output terminal 230, and outputs a control signal based on the comparison result. The control signal may be used to control the start or stop of an integrated circuit (IC). The detection and output circuit 700 may also output a characteristic of the input signal based on the comparison result, for example, to indicate whether the type of the input signal is AC or DC. As an example, the detection and output circuit 700 may include at least one counting circuit. As an example, the counting circuit may include one or more counters for determining whether the type of the input signal is AC or DC by counting the number of flips of the output of the comparator between high and low levels.

One terminal of the latch circuit 800 may be connected to the comparator output terminal 230 of the comparator 200 and the other terminal thereof is connected to a voltage bias circuit 110. The latch circuit 800 records and latches peak data of the V_(HV) according to the output signal of the comparator output terminal 230 of the comparator, and transfers the peak data to the voltage bias circuit 110. The voltage bias circuit 110 automatically adjusts the magnitude of a bias voltage according to the peak data.

The voltage adjustment circuit 100 may include an input terminal 101, the first output terminal 102 and the second output terminal 103. The input terminal 101 of the voltage adjustment circuit receives the operating voltage V₀. The first output terminal 102 of the voltage adjustment circuit outputs the first voltage V₁. The second output terminal 103 of the voltage adjustment circuit outputs the second voltage V₂ that is a stepped voltage. As an example, the second voltage V₂ is different from the first voltage V₁ by a bias voltage, i.e., ΔV, at the beginning of a preset clock period T_(sample), and the second voltage does not drop by more than a first amplitude in the clock period T_(sample). For example, the first amplitude may be 1%, 2%, 3%, 4%, 5%, 6%, 7%, 8%, 9% or 10%, or an interval between any two of the foregoing numbers, of ΔV. The magnitude of the bias voltage ΔV is related to the first voltage V₁.

Specifically, the voltage adjustment circuit 100 may include a voltage bias circuit 110 and a step voltage generating circuit 500.

The voltage bias circuit 110 may add the bias voltage ΔV to an input voltage V_(in) of the voltage bias circuit 110 and output a voltage V_(out). As an example, the voltage bias circuit 110 may include at least one of a voltage-controlled voltage source, or a voltage-controlled current source. For example, the voltage bias circuit 110 may be a voltage-controlled current source.

As an example, the bias may be a positive bias (the bias voltage ΔV is a positive voltage), for example, the output voltage V_(out) is higher than the input voltage Vin by ΔV, that is, V_(out)=V_(in)+ΔV. The bias may also be a negative bias (the bias voltage ΔV is a negative voltage), for example, the output voltage V_(out) is lower than the input voltage V_(in) by ΔV, that is, V_(out)=V_(in)−ΔV. For ease of description, in the following description of the present disclosure, V_(out)=V_(in)+ΔV is taken as an example to illustrate the working mechanism of the rising edge detection circuit. As an example, FIG. 3A illustrates a comparison between the input voltage V_(in) and the output voltage V_(out) of the voltage bias circuit 110 according to some exemplary embodiments of the present disclosure. Referring to FIG. 3A, the input voltage V_(in) rises along the rising edge, and the voltage bias circuit 110 adds the bias voltage ΔV to V_(in) to generate V_(out).

It should be noted that FIG. 3A exemplarily describes the working process of the voltage bias circuit 110 by taking the rising edge as an example, and the mechanism is the same for the falling edge.

Referring to FIG. 1 , the step voltage generating circuit 500 may convert a voltage input to the step voltage generating circuit into a step voltage. For example, the step voltage generating circuit 500 may include a switch circuit 120, a clock circuit 300 and a voltage holding circuit 130. As an example, the switch circuit 120 may include at least one field-effect transistor (FET). As an example, the FET may include, but is not limited to, a metal oxide semiconductor field-effect transistor (MOSFET), a bipolar junction transistor (BJT), a silicon controlled rectifier (SCR), a gate turn-off thyristor (GTO), an insulated gate bipolar transistor (IGBT), a MOS-controlled thyristor (MCT), or a static induction transistor (SIT). The clock circuit 300 is connected to the switch circuit 120 and controls the switch circuit 120 to be disconnected and connected according to the clock period T_(sample) to generate the second voltage V₂. The voltage holding circuit 130 is connected to the switch circuit 120 and holds the second voltage V₂ after the switch circuit 120 is disconnected, such that the second voltage does not drop by more than the first amplitude in the clock period T_(sample). In this way, the second voltage V₂ applied to the second comparator input terminal 220 remains substantially constant during the clock period T_(sample). As an example, the voltage holding circuit 130 may include at least one capacitor circuit.

As mentioned above, the first voltage V₁ is different from the second voltage V₂ by the bias voltage ΔV at the beginning of the preset clock period T_(sample), and the second voltage does not drop by more than the first amplitude in the clock period T_(sample).

The working mechanism of the voltage fluctuation detection circuit 001 will be described below.

For ease of description, in the following description of the present disclosure, a “first circuit S1” denotes a circuit connecting the input terminal 101 and the first output terminal 102 of the voltage adjustment circuit, and a “second circuit S2” denotes a circuit connecting the input terminal 101 and the second output terminal 103 of the voltage adjustment circuit. The operating voltage signal V₀ may be transmitted to the first comparator input terminal 210 and the second comparator input terminal 220 via the first circuit S1 and the second circuit S2, respectively. Referring to FIG. 1 , an input terminal of the first circuit S1 is electrically connected to the operating voltage V₀, and an output terminal thereof is the first output terminal 102 of the voltage adjustment circuit. The first circuit S1 may convert the operating voltage V₀ into the first voltage V₁. An input terminal of the second circuit S2 is electrically connected to the operating voltage V₀, and an output terminal thereof is the second output terminal 103 of the voltage adjustment circuit. The second circuit S1 may convert the operating voltage V₀ into the second voltage V₂.

Referring to FIG. 1 , the voltage divider circuit 400 divides the input signal V_(HV) into the operating voltage V₀. The operating voltage V₀ is then input to the adjustment circuit 100 from the input terminal 101 of the adjustment circuit. The adjustment circuit 100 adjusts the operating voltage V₀ to the first voltage V₁ and the second voltage V₂, which are respectively output from the first output terminal 102 and the second output terminal 103 of the adjustment circuit. The first comparator input terminal 210 is a positive terminal, and the second comparator input terminal 220 is a negative terminal. The first comparator input terminal 210 of the comparator is connected to the first output terminal 102 of the adjustment circuit and receives the first voltage V₁, and the second comparator input terminal 220 of the comparator is connected to the second output terminal 103 of the adjustment circuit and receives the second voltage V₂.

The first output terminal 102 of the voltage adjustment circuit 100 is electrically connected to the input terminal 101 thereof. For example, as shown in FIG. 1 , two ends of the first circuit S1 may be directly connected to the output terminal 420 of the voltage divider circuit 400 and the first comparator input terminal 210 of the comparator. Therefore, the first voltage V₁ delivered to the first comparator input terminal 210 of the comparator via the first circuit S1 is equivalent to the operating voltage V₀ output from the output terminal of the voltage divider circuit 400, that is, V₁=V₀.

The voltage bias circuit 110 is connected in series with the step voltage generating circuit 500, and the circuits in series are respectively connected to the input terminal 101 and the second output terminal 103 of the voltage adjustment circuit. For example, as shown in FIG. 1 , the voltage bias circuit 110 and the step voltage generating circuit 500 may be connected in series and arranged on the second circuit S2. The input terminal of the voltage bias circuit 110 may be electrically connected to the output terminal 420 of the voltage divider circuit 400. The voltage bias circuit 110 may add the bias voltage to the operating voltage V₀. The voltage bias circuit 110 is configured to bias the operating voltage V₀ by ΔV. In other words, the voltage bias circuit 110 may add the bias voltage ΔV to the operating voltage V₀. The bias voltage shown in FIG. 1 is a positive voltage.

The clock circuit 300 is connected to the switch circuit 120. The clock circuit 300 sends out a clock pulse based on the preset clock period T_(sample) to control the on and off of the switch circuit 120.

One terminal of the switch circuit 120 is connected to the output terminal of the voltage bias circuit 110, and the other terminal thereof is used as the output terminal of the voltage adjustment circuit 100 and connected to the second comparator input terminal 220. When the switch circuit 120 is turned on, the second voltage V₂ output from the output terminal of the voltage bias circuit 110 may be connected to the second comparator input terminal 220. When the switch circuit 120 is turned off, the second voltage V₂ cannot be connected to the second comparator input terminal 220. As an example, the switch circuit 120 may include at least one FET or other circuit that may be controlled to turn on and off a power supply.

One terminal of the voltage holding circuit 130 is grounded (GND), and the other terminal thereof is connected to the second circuit S2 between the switch circuit 120 and the second comparator input terminal 220. The voltage holding circuit 130 is used to stabilize the second voltage V₂, which is previously applied to the second comparator input terminal 220 when the switch circuit 120 is connected, within a preset range in the preset clock period after the switch circuit 120 is disconnected. As an example, the voltage holding circuit 130 includes at least one capacitor circuit. For example, in FIG. 1 , the voltage holding circuit 130 includes a capacitor C_(hold). When the switch circuit 120 is in a connected state, the second circuit S2 is connected to apply the second voltage V₂ to the second comparator input terminal 220, and the capacitor C_(hold) is charged to the second voltage V₂. When the switch circuit is in a disconnected state, the voltage V₂ of the capacitor C_(hold) is applied to the second comparator input terminal 220 as an input signal of the second comparator input terminal 220, such that the input signal of the second comparator input terminal 220 may be stabilized at the second voltage V₂.

As an example, FIG. 3B illustrates a comparison between the voltage V_(out) of the output terminal of the voltage bias circuit and the second voltage V₂ applied to the second comparator input terminal 220 of the comparator according to some exemplary embodiments of the present disclosure (ΔV>0). FIG. 3B also shows a timing diagram of the voltage V_(in) at the input terminal of the voltage bias circuit with a dotted line.

A pulse signal m₁ occurs at time t₁. At this time, the voltage at the first comparator input terminal 210 is V₁(t₁). When the pulse signal m₁ arrives, the switch circuit 120 is connected, and the voltage at the second comparator input terminal 220 is V₂(t₁)=V₁(t₁)+ΔV. When the switch circuit 120 is connected, the capacitor C_(hold) is charged, such that the voltage across positive and negative terminals of the capacitor C_(hold) becomes V₂(t₁). After the pulse signal m₁ ends, the switch circuit 120 is disconnected. The voltage stabilizing effect of the capacitor C_(hold) causes the second voltage at the second comparator input terminal 220 to basically stabilize at V₂(t₁). The stabilization time is a clock period T_(sample) of the pulse signal, which is indicated by a horizontal line L1 in FIG. 4 . As mentioned above, the “basically stabilize” means that the voltage stabilizing effect of the capacitor C_(hold) allows the second voltage at the second comparator input terminal 220 to slightly drop on the basis of V₂(t₁). Such a drop does not exceed the first amplitude, for example, the first amplitude may be 1%, 2%, 3%, 4%, 5%, 6%, 7%, 8%, 9% or 10% of ΔV(t₁), or it may be in an interval between any two of these numbers.

A pulse signal m₂ occurs at time t₂. When the pulse signal m₂ arrives, the voltage at the first comparator input terminal 210 is V₁(t₂). The switch circuit 120 is connected again, and the voltage at the second comparator input terminal 220 increases instantaneously from V₂(t₁) to the voltage at the output terminal of the voltage bias circuit, that is, V₂(t₂)=V₁(t₂)+ΔV(t₂). When the switch circuit 120 is connected, the capacitor C_(hold) is charged, such that the voltage across positive and negative terminals of the capacitor C_(hold) becomes V₂(t₂). After the pulse signal m₂ ends, the switch circuit 120 is disconnected. The voltage stabilizing effect of the capacitor C_(hold) causes the second voltage at the second comparator input terminal 220 of the comparator to basically stabilize at V₂(t₂). The stabilization time is a clock period T_(sample) of the pulse signal, which is indicated by the horizontal line L2 in FIG. 4 . As mentioned above, the “basically stabilize” means that the voltage stabilizing effect of the capacitor C_(hold) allows the second voltage at the second comparator input terminal 220 of the comparator to slightly drop on the basis of V₂(t₂). Such a drop does not exceed the first amplitude, for example, the first amplitude may be 1%, 2%, 3%, 4%, 5%, 6%, 7%, 8%, 9% or 10% of ΔV(t₂), or it may be in an interval between any two of these numbers.

The timing of the voltage V₂ applied to the second comparator input terminal 220 of the comparator is shown in FIG. 3B. Since the magnitude of the first voltage V₁ is equivalent to that of V_(in), the relationship between the first voltage V₁ and the second voltage V₂ can be obtained. As an example, FIG. 3B also shows the timing of the first voltage V₁ applied to the first input terminal 220 of the comparator and the second voltage V₂ applied to the second comparator input terminal 220 of the comparator according to some exemplary embodiments of the present disclosure.

Referring to FIG. 3B, the switch circuit 120 receives the pulse signal m₂ of the clock circuit 300 at time t₂. The pulse signal m₂ causes the second voltage to increase from V₂(t₁) to V₂(t₂), which is indicated by a vertical line L3 in FIG. 3B. V₂ and V₁ cross at a cross point X1. The time corresponding to X1 is t₂. Before time t₂, the first voltage is above the second voltage, that is, the first voltage is higher than the second voltage. After time t₂, the first voltage is below the second voltage, that is, the first voltage is lower than the second voltage. The first voltage V₁ is applied to the first input terminal of the comparator, and the second voltage V₂ is applied to the second input terminal of the comparator. Therefore, before the clock signal m₂ arrives, the first voltage is higher than the second voltage, and the comparator output terminal 230 of the comparator 200 outputs a high level. After the clock signal m₂ ends, the first voltage is lower than the second voltage, and the comparator output terminal 230 of the comparator 200 outputs a low level. That is, when the clock signal m₂ arrives, the comparator flips from a high level to a low level. Therefore, the clock signal m₂ can cause the comparator to flip once.

Referring to FIG. 3B, as described above, the second voltage V₂ is maintained at V₂(t₂) (indicated by the horizontal line L2) in a duration from the end of the pulse signal m₂ to the arrival of a pulse signal m₃ (that is, a t₂-t₃ interval in FIG. 3B). In this duration, the first voltage V₁ continuously climbs from the cross point X₁. The first voltage and the second voltage cross again at point X2. The time corresponding to the cross point X2 is t_(x2). That is, at t_(x2), the comparator flips again. As described above, at the time corresponding to the cross point X1, the output of the comparator flips from high to low (that is, a falling edge occurs). At the time corresponding to the cross point X2, the output of the comparator is flipped from low to high (that is, a rising edge occurs). At the time t₃ when the next pulse signal m₃ arrives, the output of the comparator is flipped from high to low again (that is, a falling edge occurs again).

The second voltage V₂ is lower than the first voltage V₁ at the beginning of the clock period T_(sample). In a clock period T_(sample), when the rising amplitude of the operating voltage V₀ exceeds the bias voltage, the output of the comparator 200 undergoes at least one flip between the high and low levels.

It should be noted that the premise of the above-mentioned flip is that at the beginning of the clock period T_(sample), ΔV causes the step voltage V₂ to be higher than the voltage V₁ that naturally fluctuates with V₀. The fluctuation interval of the voltage V₁ in one clock period T_(sample) is higher than ΔV, such that V₁ crosses with V₂. Under this condition, every time a pulse signal arrives, the output of the comparator is flipped from high to low (that is, a falling edge occurs). The output of the comparator between two pulse signals is flipped from low to high (that is, a rising edge occurs). When the next pulse signal arrives, the output of the comparator is flipped from high to low again (that is, a falling edge occurs again).

As described above, when the input signal V_(HV) shown in FIG. 2A is an AC signal and V_(HV) is at the falling edge, the first voltage V₁ drops with time, and it is lower than the second voltage V₂ at the beginning of the V₁ clock period. Therefore, the second voltage V₂ is always higher than the first voltage V₁, and the output terminal of the comparator 200 always outputs a low level, and thus no flip occurs.

In summary, when V_(HV) is at the rising edge, the output of the comparator may be flipped, that is, the comparator may output a pulse. When V_(HV) is at the falling edge, the output of the comparator is not flipped, that is, the comparator does not output a pulse.

Therefore, by detecting whether the comparator can output a pulse by the detection and output circuit 700, it can be known whether the V_(HV) is currently at a rising edge or a falling edge.

In summary, the voltage fluctuation detection circuit provided by the present disclosure adds a bias to the operating voltage V₀ through the voltage bias circuit 110 in the voltage adjustment circuit 100. The bias is stored in the capacitor C_(hold) when a switch is turned on. The bias signal is sampled and held by the switch downstream of the voltage bias circuit 110, the clock signal and the capacitor C_(hold). Slopes of the first voltage signal (direct sample) applied to the first input terminal of the comparator and the second voltage applied to the second input terminal of the comparator are different, such that a crossing occurs in the clock period. The output of the comparator is flipped every time a crossing occurs. By determining whether the comparator can output a pulse signal, the fluctuation of the electrical signal can be determined, for example, whether the signal fluctuates, or whether the input signal is at a rising edge or a falling edge.

In some exemplary embodiments, the IC is only allowed to operate at the rising edge of the AC, rather than at the falling edge of the AC. To determine the time to stop the IC, the detection circuit needs to detect when the input signal changes from a rising edge to a falling edge. The input signal V_(HV) changes from a rising edge to a falling edge at a peak 901. Therefore, if the position of the peak 901 can be accurately detected, the time of the change from the rising edge to the falling edge can be known.

The detection circuit 001 provided by the present disclosure can determine the change from the rising edge to the falling edge according to the last cross point of V₁ and V₂.

Referring to FIG. 2A, when V₁ approaches the peak 901, the slope of V₁ gradually decreases. As the clock runs, the slope of V₁ gradually decreases to zero and continues to decrease to a negative value. At the end of the rising edge, as the slope of V₁ gradually decreases, the first voltage and the second voltage no longer cross, and the output of the comparator is no longer flipped. That is, the comparator no longer continuously outputs a pulse.

As an example, FIG. 2B illustrates a timing diagram of V₁ and V₂ according to some exemplary embodiments of the present disclosure; FIG. 2C is an enlarged view of curves of V₁ and V₂ in a clock period T₁ in FIG. 2B; FIG. 2D is an enlarged view of curves of V₁ and V₂ in a clock period T₂ in FIG. 2B. In the clock period T₁, V₁ and V₂ cross at the cross point X1, which is the last cross point of V₁ and V₂ at the rising edge. In the clock period T₂ immediately following the clock period T₁ and at the rising edge thereafter, V₁ and V₂ no longer cross.

Referring to FIG. 2C and FIG. 2D, in the clock period T₁, the change ΔV₁ of V₁ is higher than the bias voltage ΔV, and therefore, V₁ and V₂ cross. In the clock period T₂, the change ΔV₁ of V₁ is lower than the bias voltage ΔV, and therefore, V₁ and V₂ do not cross.

That is, in one clock period T_(sample), when the change of the operating voltage is greater than the bias voltage, V₁ and V₂ cross, and the output signal of the output terminal has at least one target flip between the high and low levels.

When the input signal rises along the rising edge, the slope of the input signal gradually decreases. Therefore, in one clock period, the change of the input signal gradually decreases until it reaches zero. The slope of the input signal at the position of the peak 901 is zero.

As described above, when the change in the operating voltage is greater than the bias voltage, V₁ and V₂ cross, and when the change in the operating voltage is less than the bias voltage, V₁ and V₂ do not cross. When the input signal rises along the rising edge, the change of the input signal gradually decreases to become zero. Since the magnitude of the bias voltage is not zero, before reaching the peak 901, V₁ and V₂ gradually change from “crossing” to “non-crossing”. Therefore, there must be a last cross point.

The position of the peak 901 can be determined according to the position of the last cross point, that is, the position of the peak 901 can be determined according to the last target flip event of the comparator.

In the duration of a rising edge, the last pulse output by the comparator corresponds to the last crossing of V₁ and V₂, that is, the time when the comparator stops outputting a pulse corresponds to the last crossing.

In summary, the circuit provided by the present disclosure can determine the change from the rising edge to the falling edge based on the time when the comparator stops outputting a pulse. The determination accuracy increases as the time of stopping the pulse output (that is, the time of the last cross point) approaches the peak.

As an example, FIG. 2E is a detailed view of a region A in FIG. 2A according to the present disclosure. Referring to FIG. 2E, when the comparator no longer outputs a pulse, a second target circuit may be triggered to monitor the output of the comparator. When the comparator starts continuous pulse output again, the second target circuit may be reset to indicate that a rising edge occurs again. In this way, the current state of the input signal V_(HV) (either at a rising edge or at a falling edge) may be determined based on the output of the second target circuit. As an example, the second target circuit may be a monitoring circuit. As an example, the monitoring circuit may include a power-on prohibition unit or a switch signal prohibition unit. In some exemplary embodiments, the power-on prohibition unit may include a hardware-based power-on prohibition circuit, and the switch signal prohibition unit may include a hardware-based switch signal prohibition circuit. In some exemplary embodiments, the monitoring circuit may also be implemented by a software-controlled general-purpose circuit, for example, the general-purpose circuit may be controlled by a power-on prohibition program or a switch signal prohibition program to complete the function of the power-on prohibition circuit or the switch signal prohibition circuit.

Based on the previous analysis, at the rising edge, the position of the last cross point of V₁ and V₂ is related to the detection accuracy of the detection circuit. The detection accuracy increases when the last cross point approaches a true peak. By selecting the appropriate bias voltage and clock period, the last cross point can be close to the true peak. In practice, the last cross point is more or less offset from the true peak. Therefore, the sampling of the circuit may more or less miss the actual peak.

In some exemplary embodiments, the power-on prohibition unit or the switch signal prohibition unit may be configured to be activated once it is detected that the comparator does not output a pulse.

Referring to FIG. 2E, the rising edge and the falling edge change at the peak 901. Before the change, it is a rising edge, and after the change, it is a falling edge. Assuming that the clock time corresponding to the peak 901 is t_(f), in one or more clock periods before the time t_(f), the first voltage and the second voltage no longer cross, and the comparator no longer outputs a pulse.

In order to improve the detection accuracy and ensure that the second target circuit starts at a falling edge, the detection and output circuit 700 may be configured as follows. When a detection result of the detection circuit shows that the comparator does not undergo the target flip in n consecutive clock periods T_(sample), the detection circuit outputs a second signal to trigger the second target circuit, the n being a natural number not less than 2. That is, when the comparator does not undergo the target flip within n consecutive clock periods, the detection and output circuit generates the second signal to indicate that the operating voltage changes from a rising edge to a falling edge, the n being a natural number not less than 2. For example, the n may be 2, 3, 4, 5, 6, 7, 8, 9 or 10, etc.

Based on the previous description, the position of the last cross point of V₁ and V₂ is related to many factors. As an example, the factors that affect the position of the last cross point of V₁ and V₂ include, but are not limited to, the magnitude of the bias voltage, the sampling frequency of the clock pulse, and the frequency and peak of the input signal. Therefore, the value of n is also related to the above factors. In a practical application, the value of n may be determined according to the magnitude of the bias voltage, the sampling frequency of the clock pulse, the frequency and peak of the input signal and the detection accuracy. In practice, the value of n in the range of 1 to 3 can enable the circuit to maintain high detection accuracy. In other words, in practice, in order to improve the detection accuracy, the time when the second target circuit is triggered may be delayed by 1 to 3 sampling periods T_(sample) from the time of the last pulse output by the comparator.

Referring to FIG. 2A, the time of triggering the second target circuit is delayed by 3 clock periods T_(sample) from the time when the comparator stops pulse output, such that the second target circuit is triggered at a falling edge. This increases the accuracy of triggering the second target circuit at a falling edge. If the second target circuit is triggered corresponding to the time of stopping the IC, the time of stopping the IC is at a falling edge and is not far from the actual peak position, which improves the detection accuracy of the circuit.

In addition to the time of stopping the IC, the detection and output circuit 700 may also determine the time of starting the IC based on the output of the comparator. Taking a switching power supply controller as an example, the switching power supply controller needs to detect an AC line voltage and determine when the AC line voltage is high enough to start the operation of the IC. When the AC line voltage is too low, the switching power supply controller must stop the switching operation so as to protect the system from excessive voltages during operation.

A start threshold V_(HV)(start) refers to a preset condition that must be met to start the operation of the IC. When the input voltage V_(HV) input to the circuit 001 via the HV pin is higher than the start threshold V_(HV)(start), the operation of the IC is started.

In some exemplary embodiments, V_(HV) may have a spike at a rising edge. Some spike may cause the input voltage V_(HV) to exceed the start threshold V_(HV)(start) in a short time. After the spike passes, the input voltage V_(HV) may return to below the start threshold V_(HV)(start) (that is, lower than the start threshold). In this case, if the IC is configured to be started immediately once it is detected that the input voltage V_(HV) exceeds the start threshold V_(HV)(start), a false start will occur. Therefore, in some exemplary embodiments of the present disclosure, the detection and output circuit 700 may be configured as follows. When a detection result of the detection and output circuit 700 shows that the comparison results all indicate that the target flips occur in N consecutive clock periods T_(sample) and the operating voltage V_(HV) is not lower than the start threshold V_(HV)(start) when each of the target flips occurring in the N consecutive clock periods occurs, the detection and output circuit 700 may output a first signal to start the IC, the N being a natural number not less than 2. For example, the N may be 2, 3, 4, 5, 6, 7, 8, 9 or 10, etc. As an example, the first signal may be configured to control the start of a first target circuit. As an example, the first target circuit may include an IC. As an example, the IC may include a flyback converter.

That is, according to the circuit provided by the present disclosure, the IC is started only when the following two conditions are met at the same time.

Condition 1: The comparison results output by the comparator 200 in the N consecutive clock periods T_(sample) respectively include a target flip.

Condition 2: The operating voltage V_(HV) is not lower than the start threshold V_(HV)(start) when each of the target flips occurring in the N consecutive clock periods occurs.

For ease of understanding, in the following description of the present disclosure, N=2 is taken as an example to describe the circuit.

As an example, FIG. 2F illustrates a timing diagram of various signals of another voltage rising edge detection circuit in operation according to some exemplary embodiments of the present disclosure. Referring to FIG. 2F, a spike J in V_(HV) causes V_(HV) to exceed V_(HV)(start) at time t_(J), and after the spike J goes away, V_(HV) returns to below V_(HV)(start). If the IC is started immediately once it is detected that the input voltage V_(HV) exceeds the start threshold V_(HV)(start), that is, the IC is started at t_(J), a false start will occur.

As discussed above, the circuit provided by the present disclosure can only start the IC when Condition 1 and Condition 2 are met at the same time. Taking N=2 as an example, it can be understood that, in order to avoid a false start, the IC must sample two consecutive AC line voltages which are higher than the start threshold before the start operation.

Specifically, in FIG. 2F, the spike J enables V_(HV) to exceed the start threshold V_(HV)(start) at time L. The output results of the comparator have a target flip in two consecutive clock periods (the clock periods T₁ and T₂) since the V_(HV) exceeding the start threshold V_(HV)(start). Based on the above description, the target flip in the clock period T₁ corresponds to the time when the cross point X1 appears, and the target flip in the clock period T₂ corresponds to the time when the cross point X2 appears. Referring to FIG. 2F, V_(HV) is lower than V_(HV)(start) at the time t_(X1) when the cross point X1 appears, and V_(HV) is higher than V_(HV)(start) at the time t_(X2) when the cross point X2 appears.

In other words, Condition 1 is met, that is, in the two clock periods (the clock periods T₁ and T₂) since the V_(HV) exceeds the start threshold V_(HV)(start), the output results of the comparator respectively undergo a target flip. However, Condition 2 is not met, that is, when the first target flip of the two target flip occurs, the corresponding V_(HV) is lower than V_(HV)(start). Therefore, the IC cannot be started. In this way, a false start is avoided.

In the two consecutive clock periods T₂ and T₃, the output results of the comparator in the two consecutive clock periods have a target flip. According to the above discussion, in the two consecutive clock periods of T₂ and T₃, the first target flip corresponds to the time of the cross point X2, and the second target flip corresponds to the time of the cross point X3. At the time t_(X2) when the cross point X2 appears and the time t_(X3) when the cross point X2 appears, V_(HV) is higher than V_(HV)(start). That is, in the two consecutive clock periods T₂ and T₃, the input signal V_(HV) meets both Condition 1 and Condition 2. Therefore, the IC can be started. In this way, the accuracy of the circuit is improved.

As an example, FIG. 2G illustrates a structure of the detection and output circuit 700 according to some exemplary embodiments of the present disclosure. Referring to FIG. 2G, the detection and output circuit 700 may include a comparator 710, an AND circuit 720 and a counting circuit 730.

The comparator 710 is configured to compare V_(HV) and V_(HV)(start). When V_(HV) is higher than V_(HV)(start), the comparator 710 outputs a high level, and when V_(HV) is lower than V_(HV)(start), the comparator 710 outputs a low level.

The output terminal of the rising edge trigger circuit 600 is connected to a first input terminal of the AND circuit 720. For the rising edge trigger circuit 600 shown in FIG. 1 , the output of the comparator 200 is the output of the rising edge trigger circuit 600. Based on the above description, when the input signal V_(HV) is an AC signal and is at a rising edge, the comparator 200 may output a pulse with a target flip (as shown in FIG. 2F).

Referring to FIG. 2G, an output terminal of the comparator 710 is connected to a second input terminal of the AND circuit 720.

According to the circuit structure shown in FIG. 2G, the timing shown in FIG. 2F and the principle of the AND circuit 720, it can be understood that a pulse output by the comparator 200 is used as a sampling pulse to perform a target sampling on a comparison result of the comparator 710. The time when each sampling pulse in the target sampling occurs corresponds to the time when the target flip occurs, that is, the time when the cross points X1, X2 and X3 shown in FIG. 2F appear. When a sampling result corresponding to a sampling pulse is a high level, it means that the input signal V_(HV) is higher than V_(HV)(start) when the target flip occurs, that is, V_(HV) is higher than V_(HV)(start) when the cross point appears. An output signal of the AND circuit 720 represents a result of this sampling. That is, when the AND circuit 720 outputs a high level, it means that V_(HV) is higher than V_(HV)(start) when the corresponding cross point appears. Conversely, when the AND circuit 720 outputs a low level, it means that V_(HV) is lower than V_(HV)(start) when the corresponding cross point appears.

An input terminal of the counting circuit 730 is connected to the output terminal of the AND circuit 720, and an output terminal of the counting circuit 830 is connected to a first target circuit 790. As an example, the first target circuit 790 is a flyback converter. The counting circuit 730 is configured to count the number of pulses output by the AND circuit 720. If a counting result of the counting circuit 730 shows that the AND circuit 720 respectively outputs a pulse in two consecutive clock periods T_(sample), it means that the output of the comparator 200 in the two consecutive clock periods respectively undergoes a target flip, and when the target flip occurs, the corresponding V_(HV) is higher than V_(HV)(start). Therefore, the IC can be started. In summary, a false start can be avoided by sampling two continuous AC line voltages which are higher than the start threshold before starting the IC.

It should be noted that the above only lists the two conditions that must be met to start the IC. In actual applications, there may be other conditions for starting the IC without affecting the core principle of the present disclosure. For example, in the circuit structure shown in FIG. 2G, the input terminal of the AND circuit 720 may also be connected to signals corresponding to other conditions.

In some exemplary embodiments, the magnitude of ΔV is constant, regardless of the characteristic of the input voltage V_(in).

As an example, FIG. 4A illustrates a comparison of outputs corresponding to two different inputs V_(HV) ¹ and V_(HV) ² under a constant ΔV according to some exemplary embodiments of the present disclosure.

FIG. 4A shows three diagrams in sequence from left to right. In the three diagrams, the sampling clock period is T_(sample). In the left diagram of FIG. 4A, a corresponding input signal is V_(HV) ¹, and a corresponding bias voltage is ΔV. In the middle diagram of FIG. 4A, a corresponding input signal is V_(HV) ², and a corresponding bias voltage is ΔV. In the right diagram of FIG. 4A, a corresponding input signal is V_(HV) ², and a corresponding bias voltage is ΔV′. In FIG. 4A, the peak of the signal V_(HV) ² is higher than that of the signal V_(HV) ¹, and ΔV′ is higher than ΔV.

Referring to the left diagram in FIG. 4A, when the input signal is V_(HV) ¹, in a clock period T(1), V1 and V2 cross (cross point X1), and the comparator outputs a pulse. In a clock period T(2), V1 and V2 cross (cross point X2), and the comparator outputs a pulse. In a clock period T(3), V1 and V2 do not cross, and the comparator stops outputting a pulse. According to the above description, the detection and output circuit 700 determines whether the input signal V_(HV) is currently at a rising edge or a falling edge by determining whether the comparator can output a pulse. If the detection and output circuit 700 is configured to output a signal indicating a falling edge when a next clock pulse (corresponding to a pulse m4 at t4 in the left diagram of FIG. 4A) arrives after the comparator stops outputting a pulse, then, as shown in the left diagram of FIG. 4A, the detection and output circuit 700 outputs a signal at t4 to indicate that the V_(HV) changes from a rising edge to a falling edge. As an example, if a second target circuit is used to monitor the output of the comparator, when the pulse m4 at time t4 arrives, the output of the second target circuit undergoes a flip.

Referring to the middle diagram of FIG. 4A, when the input signal is V_(HV) ², V1 and V2 cross (cross point Y1) in the clock period T(1), and the comparator outputs a pulse. Since the clock period T(2), V1 and V2 do not cross, and the comparator stops outputting a pulse. According to the above description, the detection and output circuit 700 determines whether the input signal V_(HV) is currently at a rising edge or a falling edge by determining whether the comparator may output a pulse. Similarly, if the detection and output circuit 700 is configured to output a signal indicating a falling edge when a next clock pulse (corresponding to a pulse m3 at t3 in the middle diagram of FIG. 4A) arrives after the comparator stops outputting a pulse, then, as shown in the middle diagram of FIG. 4A, the detection and output circuit 700 outputs a signal at t3 to indicate that the V_(HV) changes from a rising edge to a falling edge. As an example, if a second target circuit is used to monitor the output of the comparator, when the pulse m3 at time t3 arrives, the output of the second target circuit undergoes a flip.

The left diagram of FIG. 4A is compared with the middle diagram of FIG. 4A. When the input signal is V_(HV) ² with a small peak, if the same bias voltage ΔV is used, compared with the left diagram of FIG. 4A, the middle diagram of FIG. 4A shows that the time when the second target circuit undergoes a flip has a long wavelength band from a peak 901 of V_(HV) ². That is, when the second target circuit undergoes a flip, V_(HV) ² actually has a long wavelength band before it changes from a rising edge to a falling edge. This is because when the peak of the input signal V_(HV) ² is small, its initial slope is also small. In this case, if it is determined directly according to the output result of the comparator that the rising edge is ended and the falling edge is started, the detection accuracy of the circuit is not very high.

In some exemplary embodiments, the magnitude of ΔV may be related to V_(in).

As an example, the magnitude of ΔV may be positively correlated with the peak of V_(in). That is, if the peak of V_(HV) is lower than that of V_(HV), then the value of ΔV₂ is lower than that of ΔV₁. As an example, FIG. 4B illustrates a relationship between ΔV and the peak of V_(in) according to some exemplary embodiments of the present disclosure. In the exemplary embodiments shown in FIG. 4B, ΔV=K·(peak of V_(in)), where K is a constant value, that is, ΔV has a linear positive correlation with the peak of V_(HV). It should be noted that FIG. 4B is only an example to describe the positive correlation between ΔV and the peak of V_(HV). The positive correlation between ΔV and the peak of V_(HV) may also be non-linear without affecting the core spirit of the present disclosure. For example, FIG. 4C illustrates another relationship between ΔV and the peak of V_(in) according to some exemplary embodiments of the present disclosure. In FIG. 4C, ΔV is positively, but not linearly correlated with the peak of V_(HV). Of course, in some exemplary embodiments, the magnitude of ΔV may also change in real time with V_(in). For example, ΔV(t)=K·V_(in)(t).

Referring to FIG. 4A, as shown in the right diagram of FIG. 4A, when the input signal is V_(HV) ² with a small peak, if a small bias voltage ΔV′ is used, in a clock period T(1), V1 and V2 cross (cross point Z1), and the comparator outputs a pulse. In a clock period T(2), V1 and V2 cross (cross point Z2), and the comparator outputs a pulse. Since a clock period T(3), V1 and V2 do not cross, and the comparator stops outputting a pulse. According to the above description, the detection and output circuit 700 determines whether the input signal V_(HV) is currently at a rising edge or a falling edge by determining whether the comparator outputs a pulse. Similarly, if the detection and output circuit 700 is configured to output a signal indicating a falling edge when a next clock pulse (corresponding to a pulse m4 at t4 in the right diagram of FIG. 4A) arrives after the comparator stops outputting a pulse, then, as shown in the right diagram of FIG. 4A, the detection and output circuit 700 outputs a signal at t4 to indicate that the V_(HV) changes from a rising edge to a falling edge. As an example, if the second target circuit is used to detect the output of the comparator, when the pulse m4 at time t4 arrives, the output of the second target circuit undergoes a flip.

The middle diagram of FIG. 4A is compared with the right diagram of FIG. 4A. When the input signal is V_(HV) with a small peak, if a small bias voltage ΔV′ is used, compared with the middle diagram of FIG. 4A, the right diagram of FIG. 4A shows that the time when the output signal of the second target circuit is flipped is delayed backward by one clock period T_(sample). Compared with the middle diagram of FIG. 4A, in the right diagram, the input signal V_(HV) corresponding to the time when the output signal of the second target circuit is flipped is closer to the peak 901, which improves the detection accuracy of the circuit.

In summary, the voltage detection circuit provided by the present disclosure can detect the voltage of the AC line.

Firstly, the circuit has a simple structure and a small number of components, which can reduce the cost and volume of the IC.

In addition, the circuit has high accuracy and can achieve a balance between the circuit complexity, detection accuracy, detection speed and low cost, so as to achieve a balance between the optimal performance and the cost of the IC. For example, only by reasonably setting the value of ΔV and the frequency of the sampling clock T_(sample), the frequency of the pulse output by the comparator can be controlled.

Further, for an analog IC (including, but not limited to, a switching power supply controller, an audio/video amplifier or a signal converter), if a digital circuit is used to sample and detect the characteristic of the electrical signal, the addition of a digital design to the analog IC will increase the cost of the IC. In the detection circuit provided by the present disclosure, the input signal V_(HV) may be an analog signal. When the detection circuit is applied to the analog IC, it can greatly reduce the complexity of the analog IC, and can achieve a balance between the circuit complexity, detection accuracy, sufficiently fast detection speed and low cost, so as to achieve a balance between the optimal performance and the cost of the IC.

It should be noted that, in the above description, the principle of the voltage fluctuation detection circuit provided in this disclosure is introduced by taking the rising edge as an example. The voltage fluctuation detection circuit provided by this disclosure can also detect the falling edge so as to detect the input signal. In the case where the input signal is at the falling edge, if the circuit is such constructed that the first voltage is higher than the second voltage at the beginning of the clock period T_(sample) and the falling amplitude (decrease) of the first voltage V₁ exceeds the bias voltage value within one clock period, the output of the comparator is flipped at least once. For example, the bias voltage in FIG. 1 can be set as −ΔV. In this case, the first voltage is higher than the second voltage at the beginning of the clock period T_(sample), and in one clock period, when the falling amplitude of the first voltage V₁ exceeds the bias voltage amplitude ΔV, the output of the comparator 200 is flipped at least once.

FIG. 5 illustrates a structure of a voltage fluctuation detection circuit according to some exemplary embodiments of the present disclosure.

Referring to FIG. 5 , the voltage bias circuit 110 is provided on the first circuit S1. The voltage bias circuit 110 is connected in series with the first output terminal 102 and the input terminal 101 of the adjustment circuit. That is, two ends of the voltage bias circuit 110 are respectively connected to the output terminal 101 and the first output terminal 102 of the adjustment circuit.

The step voltage generating circuit 500 is provided on the second circuit S2. The step voltage generating circuit 500 is connected in series with the input terminal 101 and the second output terminal 103 of the adjustment circuit. That is, two ends of the step voltage generating circuit 500 are respectively connected to the output terminal 101 and the second output terminal 103 of the adjustment circuit. Referring to FIG. 5 , the first comparator input terminal 210 of the comparator is a positive terminal, the second comparator input terminal 220 of the comparator is a negative terminal, and the bias voltage is a negative voltage −ΔV.

As an example, FIG. 6 illustrates a comparison between the operating voltage V₀, the first voltage V₁ and the second voltage V₂ in the structure of the circuit shown in FIG. 5 .

The voltage bias circuit 110 adds a bias voltage to the operating voltage V₀ to generate the first voltage V₁. The bias voltage is negative, and its absolute value is equal to ΔV, that is, the bias voltage is −ΔV. Therefore, V₁=V₀−ΔV. The timing of the first voltage V₁ is indicated by V₁ in FIG. 6 .

The step voltage generating circuit 500 acts on the operating voltage signal V₀ to cause the operating voltage signal V₀ to step so as to generate a stepped second voltage V₂.

Referring to FIGS. 5 and 6 , a switch Q₁ is turned on when the clock pulse m₁ arrives. The second voltage V₂ is equal to the operating voltage V₀, which is V₂(t₁). When the switch Q₁ is turned on, the capacitor C_(hold) is charged to V₂(t₁). After the clock pulse m₁ ends, the switch Q₁ is turned off. The capacitor C_(hold) keeps the voltage on the negative terminal of the comparator basically at V₂(t₁) (indicated by the horizontal line L1 in FIG. 6 ), and the holding time is one clock period T_(sample) of the clock pulse. The “basically stabilize” means that the voltage stabilizing effect of the capacitor C_(hold) allows the second voltage at the second comparator input terminal 220 of the comparator to slightly drop on the basis of V₂(t₁). Such a drop does not exceed the first amplitude, for example, the first amplitude may be 1%, 2%, 3%, 4%, 5%, 6%, 7%, 8%, 9% or 10% of ΔV(t₁), or may be in an interval between any two of these numbers. It can be seen from FIG. 6 that the first voltage V₁ is lower than the second voltage V₂ at the beginning of the corresponding clock period T_(sample) indicated by the horizontal line L1. In the clock period T_(sample), the operating voltage V₀ rises along the rising edge, the first voltage V₁ also rises along the rising edge, but the second voltage V₂ remains substantially constant under the action of the capacitor C_(hold). In this clock period, as the first voltage V₁ rises, the first voltage V₁ and the second voltage V₂ cross (cross point X1), and the comparator undergoes a flip.

When the clock pulse m₂ arrives, the switch Q₁ is connected, and the second voltage V₂ instantaneously increases to the operating voltage V₀, that is, V₂(t₂). Before the clock pulse m2 arrives, the magnitude of the second voltage V₂ is V₂(t₁). The arrival of the clock pulse m2 causes the second voltage V₂ to instantaneously rise from V₂(t₁) to V₂(t₂). Before the rise, the magnitude of the second voltage, i.e. V₂(t₁), is lower than that of the first voltage V₁, that is, the voltage on the positive terminal of the comparator is higher than that on the negative terminal, and the comparator outputs a high level. After the rise, the magnitude of the second voltage V₂(t₂) is higher than that of V₁, that is, the voltage on the positive terminal of the comparator is lower than that on the negative terminal, and the comparator outputs a low level. That is, the arrival of the clock pulse m₂ causes the first voltage V₁ and the second voltage V₂ to cross once (cross point X2), and the comparator flips once.

Meanwhile, when the clock pulse m₂ arrives and the switch Q₁ is turned on, the capacitor C_(hold) is charged, such that the voltage across the positive and negative terminals of the capacitor C_(hold) becomes V₂(t₂). After the clock pulse m₂ ends, the switch Q₂ is turned off. The capacitor C_(hold) keeps the second voltage V₂ applied to the negative terminal of the comparator at V₂(t₂) (indicated by the horizontal line L2 in FIG. 6 ), and the holding time is one clock period T_(sample) of the clock pulse.

In summary, a negative bias voltage can also be used to make the first voltage and the second voltage cross in the clock period and make the comparator flip. Thus, it can also be determined whether the input signal is a DC signal or an AC signal by determining the output of the comparator (for example, whether the comparator can output a pulse and the number of output pulses).

It should be noted that, for ease of description, in the above description, the principle of the voltage rising edge detection circuit is described with the first input terminal of the comparator as a positive terminal and the second input terminal of the comparator as a negative terminal. The first input terminal of the comparator may also be a negative terminal and the second input terminal of the comparator may also be a positive terminal without affecting the core principle of the present disclosure.

In addition, the bias voltage in FIG. 5 can also be set to +ΔV for detecting the falling edge of the operating voltage V₀. In this case, the first voltage is higher than the second voltage at the beginning of the clock period T_(sample), and when the falling amplitude of the first voltage V₁ exceeds the bias voltage value amplitude ΔV within one clock period, the output of the comparator 200 is flipped at least once.

FIG. 7 illustrates a structure of a voltage fluctuation detection circuit 003 according to some exemplary embodiments of the present disclosure. The circuit structure shown in FIG. 7 is similar to that shown in FIG. 1 , except that in FIG. 7 , the first output terminal of the voltage adjustment circuit is connected to the first input terminal of the comparator, and the first input of the comparator is a negative terminal of the comparator. In addition, in FIG. 7 , the second output terminal of the voltage adjustment circuit is connected to the second input terminal of the comparator, and the second input terminal of the comparator is a positive terminal of the comparator. That is, the voltage bias circuit 110 is connected in series with the step voltage generating circuit 500 and is provided on the first circuit S1. Therefore, the first voltage is applied to the negative terminal of the comparator, and the second voltage is applied to the positive terminal of the comparator.

The comparison between the first voltage and the second voltage illustrated in FIG. 3B is applicable to the circuit structure shown in FIG. 7 . Referring to FIG. 3B, in the circuit structure shown in FIG. 7 , for every clock period that comes, the comparator flips once at the arrival of the clock period and flips again during the clock period. In the circuit structure shown in FIG. 7 , taking the clock signal m₂ as an example, before the clock signal m₂ arrives, the second voltage V₂(t₁) is lower than the first voltage V₁, that is, the voltage on the positive terminal of the comparator is lower than that on the negative terminal, and the comparator outputs a low level. The arrival of the clock pulse m₂ causes the second voltage to rise instantaneously from V₂(t₁) to V₂(t₂). After the rise, the second voltage V₂(t₂) is higher than the first voltage V₁, that is, the voltage on the positive terminal of the comparator is higher than that on the negative terminal of the comparator, and the comparator outputs a high level. That is, the arrival of the pulse signal m₂ causes the comparator to flip from a low level to a high level. After the pulse signal m₂ ends, the second voltage is maintained at V₂(t₂) under the action of the capacitor C_(hold). As the first voltage rises along the rising edge, the second voltage and the first voltage cross again (cross point X2). Before the cross point X2, the second voltage is higher than the first voltage, that is, the voltage on the positive terminal of the comparator is higher than that on the negative terminal of the comparator, and the comparator outputs a high level. After the cross point X2, the second voltage is lower than the first voltage, that is, the voltage on the positive terminal of the comparator is lower than that on the negative terminal of the comparator, and the comparator outputs a low level. That is, in the clock period T_(sample), the comparator flips from a high level to a low level.

When the clock pulse arrives, the comparator flips from a low level to a high level, and before the next clock pulse arrives, the comparator flips from a high level to a low level. Therefore, it can also be determined whether the input signal is a DC signal or an AC signal by determining the output of the comparator (for example, whether the comparator can output a pulse and the number of output pulses).

In addition, the bias voltage in FIG. 7 can also be set to −ΔV for detecting the falling edge of the operating voltage V₀. In this case, the first voltage is higher than the second voltage at the beginning of the clock period T_(sample), and when the falling amplitude of the first voltage V₁ exceeds the bias voltage value amplitude ΔV within one clock period, the output of the comparator 200 is flipped at least once.

FIG. 8 illustrates a structure of a voltage fluctuation detection circuit 004 according to some exemplary embodiments of the present disclosure. The circuit structure shown in FIG. 8 is similar to that shown in FIG. 5 , except that in FIG. 8 , the first output terminal of the voltage adjustment circuit is connected to the first input terminal of the comparator, and the first input of the comparator is a negative terminal of the comparator. In addition, in FIG. 8 , the second output terminal of the voltage adjustment circuit is connected to the second input terminal of the comparator, and the second input terminal of the comparator is a positive terminal of the comparator. In other words, the first voltage is applied to the negative terminal of the comparator, and the second voltage is applied to the positive terminal of the comparator. The analysis of FIG. 8 may be referred to that of FIG. 5 , which will not be repeated herein for the sake of brevity.

In summary, the voltage fluctuation detection circuit provided by the present disclosure adds a bias to the operating voltage V₀ through the voltage bias circuit 110 in the voltage adjustment circuit 100. The bias is stored in the capacitor C_(hold) when the switch is turned on. The bias signal is sampled and held by the switch downstream of the voltage bias circuit 110, the clock signal and the capacitor C_(hold). Slopes of the first voltage signal (direct sample) applied to the first input terminal of the comparator and the second voltage applied to the second input terminal of the comparator are different, such that a crossing occurs in the clock period. The output of the comparator is flipped every time a crossing occurs. By determining whether the comparator can output a pulse signal, the fluctuation of the electrical signal can be determined, for example, whether the electrical signal fluctuates, or whether the electrical signal is at a rising edge or a falling edge.

The voltage fluctuation detection circuit provided by the present disclosure can detect the voltage of an AC line. The circuit has a simple structure and a small number of components, which can reduce the cost and volume of the IC. The circuit has high accuracy and can achieve a balance between the circuit complexity, detection accuracy, sufficiently fast detection speed and low cost, so as to achieve a balance between the optimal performance and the cost of the IC. For example, the frequency of the pulse output by the comparator can be controlled only by reasonably setting the value of ΔV and the frequency of the sampling clock T_(sample).

For an analog IC (including, but not limited to, a switching power supply controller, an audio/video amplifier or a signal converter), if a digital circuit is used to sample and detect the characteristic of the electrical signal, the addition of a digital design to the analog IC will increase the cost of the IC. In the detection circuit provided by the present disclosure, the input signal V_(HV) may be an analog signal. When the detection circuit is applied to the analog IC, it can greatly reduce the complexity of the analog IC, and can achieve a balance between the circuit complexity, detection accuracy, sufficiently fast detection speed and low cost, so as to achieve a balance between the optimal performance and the cost of the IC.

The voltage fluctuation rising edge detection circuit provided by the present disclosure can be used in an AC-DC controller. The voltage fluctuation rising edge detection circuit can detect whether the operating current of the AC-DC controller is AC or DC, thereby expanding the operating current of the AC-DC controller from DC to DC and AC.

The basic concepts are described above, and those skilled in the art may better understand, after reading this detailed disclosure, that the above detailed disclosure is intended to be presented by way of example only and not limitation. Although it is not explicitly stated herein, those skilled in the art may make various changes, improvements and modifications to the present disclosure. For example, the steps in the method of the present disclosure may not necessarily be performed in exactly the order described. These steps may also be performed in part and/or in other combinations as reasonably expected by those of ordinary skill in the art. These changes, improvements and modifications are intended to be included in the present disclosure, and fall within the scope of the embodiments of the present disclosure.

In addition, some terms are used to describe the embodiments of the present disclosure. For example, the terms “an embodiment”, “one embodiment” and/or “some exemplary embodiments” mean that a particular feature, structure or characteristic described in the embodiment(s) is included in at least one embodiment of the present disclosure. Therefore, it should be emphasized and understood that two or more references to “an embodiment”, “one embodiment” or “an alternative embodiment” in various parts of this disclosure may not necessarily all refer to the same embodiment. In addition, the specific features, structures or characteristics may be appropriately combined in one or more embodiments of the present disclosure.

In addition, those skilled in the art should understand that the aspects of the present disclosure may be described herein in either form of many patentable categories or contexts. These categories and contexts include any new and useful processes, machines, manufacturing or composition issues, or any new and useful improvements.

Correspondingly, various aspects of the present disclosure may be fully implemented in hardware or software (including firmware, resident software, microcode, etc.). Alternatively, the software and hardware implementations may be combined, and all of them are generally referred to herein as “blocks”, “modules”, “engines”, “units”, “components” or “systems”. In addition, the aspects of the present disclosure may take the form of a computer program product embodied in one or more computer-readable media on which computer-readable program codes are present.

Further, the stated order of processing elements or sequences, and the numbers, letters or other names used accordingly, are not intended to limit the claimed processes and methods to any order, unless it is defined in the claims. Although various embodiments have been discussed above through various embodiments that are currently considered to be useful embodiments of the present disclosure, it should be understood that such details are only for such a purpose. The appended claims are not limited to the disclosed embodiments, and on the contrary, they are intended to cover modifications and equivalent arrangements made within the scope of the disclosed embodiments. For example, although the implementation of the various components described above can be embodied in a hardware device, it can also be implemented as a software-only solution, for example, an installation on an existing server or mobile device.

Similarly, it should be understood that in the above description of the exemplary embodiments of the present disclosure, various features are sometimes combined in a single embodiment, drawing or description thereof to simplify the present disclosure and make one or more of the various creative embodiments better understood. However, the method of the present disclosure should not be interpreted as reflecting an intention that the claimed subject matter requires more features than those explicitly recited in each claim. In contrast, an inventive embodiment may have fewer features than all the features of a single previously disclosed exemplary embodiment. 

What is claimed is:
 1. A voltage fluctuation detection circuit, comprising: a rising edge trigger circuit, including an input terminal and an output terminal, wherein the rising edge trigger circuit detects an operating voltage received by the input terminal with a preset clock period, when a change of the operating voltage within the preset clock period is greater than a preset bias voltage, an output signal of the output terminal undergoes at least one target flip between a high level and a low level; and a detection and output circuit, connected to the output terminal of the rising edge trigger circuit, and configured to detect the change of the operating voltage and the target flip, and output a control signal according to a detection result, wherein when the detection result of the detection and output circuit indicates that an output signal of the rising edge trigger circuit always undergoes the target flip in N consecutive preset clock periods, and the operating voltage is always not less than a starting threshold value when each target flip of all the target flips occurring in the N consecutive preset clock periods, wherein the detection and output circuit generates an first signal, where N is a natural number not less than
 2. 2. The voltage fluctuation detection circuit according to claim 1, wherein the first signal is configured to control to start a first target circuit.
 3. The voltage fluctuation detection circuit according to claim 1, wherein when the output signal of the rising edge trigger circuit does not undergoes the target flips in n consecutive clock periods, the detection and output circuit generates a second signal for indicating that the operating voltage has been converted from a rising edge to a falling edge, wherein n is a natural number not less than
 2. 4. The voltage fluctuation detection circuit according to claim 3, wherein the detection and output circuit comprises a second target circuit, when the output signal of the rising edge trigger circuit does not undergoes the target flip in n consecutive clock periods, the second target circuit is triggered to indicate that the operating voltage has been converted from rising edge to falling edge.
 5. The voltage fluctuation detection circuit according to claim 1, wherein the rising edge trigger circuit includes: an adjustment circuit, including: an adjustment circuit input terminal to receive the operating voltage as an AC voltage, a first adjustment circuit output terminal to output a first voltage, and a second adjustment circuit output terminal to output a second voltage that is stepped; and a comparator, including: a first comparator input terminal to receive the first voltage, a second comparator input terminal to receive the second voltage, and a comparator output terminal to output a comparison result of the first voltage and the second voltage, wherein the second voltage is different from the first voltage by the bias voltage at the beginning of the clock period, and the second voltage does not drop by more than a first voltage drop in the clock period.
 6. The voltage fluctuation detection circuit according to claim 5, wherein a magnitude of the bias voltage is positively correlated with an amplitude of the first voltage.
 7. The voltage fluctuation detection circuit according to claim 5, wherein the target flip includes a flip from a low level to a high level; when the first voltage is lower than the second voltage at the beginning of the preset clock period, the comparator outputs the low level; and in the preset clock period, when an increase of the first voltage exceeds the bias voltage value, the output of the comparator is flipped from the low level to the high level.
 8. The voltage fluctuation detection circuit according to claim 5, wherein the target flip includes flip from a low level to a high level; when the first voltage is higher than the second voltage at the beginning of the preset clock period, the comparator outputs the high level; and in the preset clock period, when a decrease of the first voltage exceeds the bias voltage value, the output of the comparator is flipped from the high level to the low level.
 9. The voltage fluctuation detection circuit according to claim 5, wherein the adjustment circuit further includes: a voltage bias circuit, configured to add the bias voltage to an input voltage of the voltage bias circuit; and a step voltage generating circuit, configured to convert a voltage input to the step voltage generating circuit into a step voltage.
 10. The voltage fluctuation detection circuit according to claim 9, wherein the step voltage generating circuit includes: a switch circuit; a clock circuit, connected to the switch circuit and controlling the switch circuit to be disconnected or connected according to the clock period to generate the second voltage; and a voltage holding circuit, connected to the switch circuit and holding the second voltage after the switch circuit is disconnected, such that the second voltage does not drop by more than the first voltage drop in the clock period.
 11. The voltage fluctuation detection circuit according to claim 10, wherein the voltage bias circuit includes at least one of a voltage-controlled voltage source and a voltage-controlled current source; the switch circuit includes at least one field-effect transistor (FET); and the voltage holding circuit includes at least one capacitor.
 12. The voltage fluctuation detection circuit according to claim 9, wherein the first adjustment circuit output terminal is electrically connected to the adjustment circuit input terminal; and the voltage bias circuit is connected in series with the step voltage generating circuit, and the circuits in series are respectively connected to the adjustment circuit input terminal and the second adjustment circuit output terminal.
 13. The voltage fluctuation detection circuit according to claim 12, wherein the first comparator input terminal is a positive terminal of the comparator, the second comparator input terminal is a negative terminal of the comparator, and the bias voltage is a positive voltage; or the first comparator input terminal is a negative terminal of the comparator, the second comparator input terminal is a positive terminal of the comparator, and the bias voltage is a positive voltage.
 14. The voltage fluctuation detection circuit according to claim 9, wherein the voltage bias circuit is connected in series with the first adjustment circuit output terminal and the adjustment circuit input terminal; and the step voltage generating circuit is connected in series with the adjustment circuit input terminal and the second adjustment circuit output terminal.
 15. The voltage fluctuation detection circuit according to claim 14, wherein the first comparator input terminal is a positive terminal of the comparator, the second comparator input terminal is a negative terminal of the comparator, and the bias voltage is a negative voltage; or the first comparator input terminal is a negative terminal of the comparator, the second comparator input terminal is a positive terminal of the comparator, and the bias voltage is a negative voltage.
 16. The voltage fluctuation detection circuit according to claim 1, further comprising: a voltage divider circuit, wherein a terminal of the voltage divider circuit is connected to an input voltage, another terminal of the voltage divider circuit is connected to a ground wire, and the voltage divider circuit divides the input voltage into the operating voltage to be output. 